Voltage controlled oscillator

ABSTRACT

An embodiment of the voltage controlled oscillator is provided. The oscillator comprises a first inductor set, a second inductor set, a second capacitor, a voltage source and a negative resistance element. The inductance of the second inductor set is k times the inductance of the first inductor set. The voltage source applies an ac voltage to the second inductor set. The negative resistance element is coupled to the second inductor set to provide a negative resistance to resonate the second capacitor at the second inductor set.

BACKGROUND OF THE INVENTION

1. Field of the Invention

The invention relates to a voltage controlled oscillator, and more particularly to a voltage controlled oscillator with a transformer.

2. Description of the Related Art

The voltage controlled oscillator is a component used as a local oscillator in many wireless communication devices. With a voltage controlled oscillator circuit, a desired frequency can be easily obtained by adjusting the charging and discharging times of capacitors or capacitive elements. For this reason, a voltage-controlled oscillator circuit is normally used in an apparatus which requires different clock frequencies. Today, CMOS integrated circuits of low power consumption have become widespread. With this trend, various voltage controlled oscillator circuits of the CMOS configuration are being developed. However, an LC tank voltage controlled oscillator usually comprises a large capacitor and a small inductor. Meanwhile, parasitic capacitor effect increases due to the small inductor, resulting in phase noise in the output clock signal of the voltage controlled oscillator.

FIG. 1 is a circuit diagram of an LC oscillator. The inductor L₁ placed in parallel with a capacitor C₁ resonates at a frequency ω=1/√{square root over (L₁C₁)}. At this frequency, the impedances of the inductor and the capacitor are equal and opposite. However, in practice, inductors or/and capacitors suffer from resistive components. For example, the series resistance of the metal wire in the inductor can be modeled as the resistor R_(s) shown in FIG. 1. An infinite quality factor Q of the inductor L₁ is defined as L₁ω/R_(s). In the FIG. 1, the equivalent impedance is given by

$\begin{matrix} {{{Z_{eq}(s)} = \frac{R_{s} + {L_{1}s}}{1 + {L_{1}C_{1}s^{2}} + {R_{s}C_{1}s}}},} & \left( {{eq}.\mspace{14mu} 1} \right) \end{matrix}$

and hence,

$\begin{matrix} {{{Z_{eq}\left( {s = {j\omega}} \right)}}^{2} = {\frac{R_{s}^{2} + {L_{1}^{2}\omega^{2}}}{\left( {1 - {L_{1}C_{1}\omega^{2}}} \right)^{2} + {R_{s}^{2}C_{1}^{2}\omega^{2}}}.}} & \left( {{eq}.\mspace{14mu} 2} \right) \end{matrix}$

The magnitude of Z_(e)q in eq. 2 reaches to a peak value in the vicinity of ω=1/√{square root over (L₁C₁)}, but the actual resonance frequency is still partially dependent on R_(s).

According to the described, controlling the resonance frequency by adjusting the capacitor C₁ and inductor L₁ should be achievable. However, in practice, the inductance of the inductor L₁ is not easily precisely adjusted, and the capacitor C₁ may suffer parasitic capacitor effect. Thus, the resonance frequency ω is unstable.

BRIEF SUMMARY OF THE INVENTION

An embodiment of the voltage controlled oscillator according to the invention is disclosed. The voltage controlled oscillator comprises a first capacitor, a first inductor, a second inductor, a third inductor, a fourth inductor, a voltage source and a negative resistance element. The first inductor comprises a first terminal coupled to the first terminal of the third inductor and a second terminal coupled to the first terminal of the first capacitor. The second inductor comprises a first terminal coupled to the first terminal of the fourth inductor and a second terminal coupled to the second terminal of the first capacitor. The second capacitor comprises a first terminal coupled to the second terminal of the third inductor and a second terminal coupled to the second terminal of the fourth inductor. The inductance of the third inductor or the fourth inductor is N times the inductance of the first inductor or the second inductor. The voltage source applies an ac voltage to the third and fourth inductors. The negative resistance element is coupled to the third and fourth inductors to provide a negative resistance.

Another embodiment of a phase locked loop device is provided. The PLL device comprises a PFD unit, a charging pump circuit, a loop filter, and a voltage controlled oscillator. The PFD unit measures a phase and a frequency difference between a reference clock signal and a feedback clock signal of the PLL device and the PFD unit outputs a difference signal UP and a difference signal DN. The charging pump circuit receives and transforms the difference signals UP and DN into a current. The loop filter receives and transforms the current into a voltage. The voltage controlled oscillator receives the voltage and outputs an output signal, wherein the voltage controlled oscillator comprises a first inductor set and a second inductor set, and the inductance of the second inductor set is k times the inductance of the first inductor set.

A detailed description is given in the following embodiments with reference to the accompanying drawings.

BRIEF DESCRIPTION OF THE DRAWINGS

The present invention can be more fully understood by reading the subsequent detailed description and examples with references made to the accompanying drawings, wherein:

FIG. 1 is a circuit diagram of an LC oscillator.

FIG. 2 is a circuit diagram of an oscillator based on an embodiment of the invention.

FIG. 3 is a circuit diagram of an oscillator based on another embodiment of the invention.

FIG. 4 is an equivalent circuit diagram of the voltage controlled oscillator shown in FIG. 2.

FIG. 5 is a schematic diagram of a phase locked loop device of an embodiment of the invention.

DETAILED DESCRIPTION OF THE INVENTION

The following description is of the best-contemplated mode of carrying out the invention. This description is made for the purpose of illustrating the general principles of the invention and should not be taken in a limiting sense. The scope of the invention is best determined by reference to the appended claims.

FIG. 2 is a circuit diagram of an oscillator based on an embodiment of the invention. The LC circuit 21 comprises an inductor L_(2a), an inductor L_(2b) and a second capacitor C₂. The inductor L_(2a) comprises a second terminal and a first terminal coupled to one terminal of the second capacitor C₂. The inductor L_(2b) comprises a first terminal coupled to another terminal of the second capacitor C₂, and a second terminal coupled to the second terminal of the inductor L₂a. The inductor L_(2a) is further connected to the inductor L_(1a), and the inductor L_(2b) is further connected to the inductor L_(1b). The inductor L_(1a) comprises a second terminal and a first terminal coupled to one terminal of the first capacitor C₁. The inductor L_(1b) comprises a first terminal coupled to another terminal of the first capacitor C₁, and a second terminal coupled to the second terminal of the inductor L₁a. In this embodiment, the inductance of the inductor L_(1a) is N times the inductance of the second inductor L_(2a), and the inductance of the inductor L_(1b) is N times the inductance of the second inductor L_(2b). In this embodiment, the inductors L_(1a), L_(1b), L_(2a) and L_(2b) receive the same voltage V_(DD). A negative resistance element 22 is coupled to the inductors L_(1a) and L_(1b) to provide a negative resistance to resonate the inductors L_(1a), L_(1b) and the first capacitor C₁. The negative resistance element 22 comprises a first transistor and a second transistor. The first transistor T1 comprises a first input terminal coupled to the first clock output terminal N1, a first output terminal, and a first control terminal coupled to the second clock output terminal N2. The second transistor T2 comprises a second input terminal coupled to the second clock output terminal N2, a second output terminal coupled to the first output terminal, and a second control terminal coupled to the first clock output terminal N1. The negative resistance element 22 further comprises a resistor R coupled between the first output terminal and ground. In this embodiment, the clock output terminal N1 and N2 are respectively coupled to the buffer 23 and 24 to output the output differential clock signal V_(out+) and V_(out−).

Without the inductors L_(2a) and L_(2b) and the second capacitor C2, the resonance frequency is ω=1/√{square root over (L₁(C₁+C_(para)))}. With the inductors L_(2a) and L_(2b) and the second capacitor C2, the resonance frequency is as followed:

$\begin{matrix} {\omega_{1} = {1/\sqrt{{L_{1}\left( {C_{1} + C_{para}} \right)}_{{refered\_ to}{\_ first}{\_ inductor}}}}} \\ {= {{1/L_{1}} \cdot \left( \frac{C_{para} + C_{1}}{N^{2}} \right)_{{refered\_ to}{\_ second}{\_ inductor}}}} \end{matrix}$

The parasitic capacitor C_(para) is generated at the input terminal of the first transistor T1. In this embodiment, only the parasitic capacitor C_(para) at the input terminal of the first transistor T1 is described for illustration, while in practice, the parasitic capacitor is also generated at the input terminal of the second transistor T2. According to the resonance frequency ω₁, the parasitic capacitor effect caused by the parasitic capacitor C_(para) can be significantly reduced. Furthermore, inductors L_(1a), L_(1b) and the capacitor C₁ adjustments are easier.

FIG. 3 is a circuit diagram of an oscillator based on another embodiment of the invention. The second inductor L₂ is further connected to a first inductor L₁. The first inductor L₁ is parallel connected to a first capacitor C₁. In this embodiment, the inductance of the first inductor L₁ is N times the inductance of the second inductor L₂. In this embodiment, the first inductor L₁ receives the voltage V_(DD), and the second inductor L₂ receives the voltage V₂. In this embodiment, the capacitors C₁ and C₂ are voltage controlled capacitors and their capacitance can be adjusted respectively by the voltages V_(DD) and V₂. The first transistor T1 and a second transistor T2 form a negative resistance element 22 which is coupled to the first inductor L₁ to provide a negative resistance to resonate the first inductor L₁ and the first capacitor C₁. The first transistor T1 comprises a first input terminal coupled to the first clock output terminal N1, a first output terminal, and a first control terminal coupled to the second clock output terminal N2. The second transistor T2 comprises a second input terminal coupled to the second clock output terminal N2, a second output terminal coupled to the first output terminal, and a second control terminal coupled to the first clock output terminal N1. The negative resistance element 22 further comprises a resistor R coupled between the first output terminal and ground. In this embodiment, the clock output terminal N1 and N2 are respectively coupled to the buffer 23 and 24 to output the output differential clock signal V_(out+) and V_(out−).

FIG. 4 is a schematic diagram of the input impedance to the voltage controlled transformer with transformer according to the invention. The input impedance Z_(IN) is derived as following.

$\begin{matrix} {Z_{IN} = {\left( {{{sL}_{2}{}\frac{1}{{sC}_{2}}} + {sL}_{1}} \right){}\frac{1}{{sC}_{1}}}} \\ {= {\left( {\frac{{sL}_{2}}{{{sL}_{2} \cdot {sC}_{2}} + 1} + {sL}_{1}} \right){}\frac{1}{{sC}_{1}}}} \\ {= {\left( {\frac{{sL}_{2}}{1 + {S^{2}L_{2}C_{2}}} + {sL}_{1}} \right){}\frac{1}{{sC}_{1}}}} \\ {= \frac{\frac{{sL}_{2}}{1 + {S^{2}L_{2}C_{2}}} + {sL}_{1}}{1 + {{sC}_{1}\left( {\frac{{sL}_{2}}{1 + {S^{2}L_{2}C_{2}}} + {sL}_{1}} \right)}}} \\ {= \frac{\left( {{sL}_{2} + {{sL}_{1}\left( {1 + {s^{2}L_{2}C_{2}}} \right)}} \right)}{\left( {1 + {s^{2}L_{2}C_{2}}} \right) + {{sC}_{1}\left( {{sL}_{2} + {{sL}_{1}\left( {1 + {s^{2}L_{2}C_{2}}} \right)}} \right)}}} \end{matrix}$

The denominator part:

(1 + s²L₂C₂) + sC₁(sL₂ + sL₁(1 + s²L₂C₂)) = 1 + s²L₂C₂ + s²(L₂ + L₁)C₁ + s⁴L₁L₂C₁C₂ = 1 + s²(L₂C₂ + L₂C₁ + L₁C₁) + s⁴L₁L₂C₁C₂ = 1 − ω²(L₂C₂ + L₂C₁ + L₁C₁) + ω⁴L₁L₂C₁C₂ $\omega^{2} = {\frac{1}{2}\left\{ \left( {{L_{2}C_{2}} + {L_{2}C_{1}} + {{L_{1}C_{1}} \pm \sqrt{\left( {{L_{2}C_{2}} + {L_{2}C_{1}} + {L_{1}C_{1}}} \right)^{2} - {4L_{1}L_{2}C_{1}C_{2}}}}} \right) \right\}}$

In this embodiment, we only consider the high frequency response portion, i.e. with “+” sign, because the inductor Q corresponding to the low frequency is too low and the voltage controlled oscillator will still be oscillated.

$\omega^{2} = {\frac{{L_{2}C_{2}} + {L_{2}C_{1}} + {L_{1}C_{1}}}{2}\left\{ {1 + \sqrt{1 - \frac{4L_{1}L_{2}C_{1}C_{2}}{\left( {{L_{2}C_{2}} + {L_{2}C_{1}} + {L_{1}C_{1}}} \right)^{2}}}} \right\}}$

Since √{square root over (1+x)}≅1+0.5x, thus,

$\begin{matrix} {\omega^{2} = {\frac{{L_{2}C_{2}} + {L_{2}C_{1}} + {L_{1}C_{1}}}{2}\left\{ {1 + 1 - \frac{2L_{1}L_{2}C_{1}C_{2}}{\left( {{L_{2}C_{2}} + {L_{2}C_{1}} + {L_{1}C_{1}}} \right)^{2}}} \right\}}} \\ {= {\left( {{L_{2}C_{2}} + {L_{2}C_{1}} + {L_{1}C_{1}}} \right)\left\{ {1 - \frac{L_{1}L_{2}C_{1}C_{2}}{\left( {{L_{2}C_{2}} + {L_{2}C_{1}} + {L_{1}C_{1}}} \right)^{2}}} \right\}}} \end{matrix}$

Assuming C₂<<C₁

$\begin{matrix} {\omega^{2} \cong {\left( {{L_{2}C_{1}} + {L_{1}C_{1}}} \right)\left\{ {1 - \frac{L_{1}L_{2}C_{1}C_{2}}{\left( {{L_{2}C_{1}} + {L_{1}C_{1}}} \right)^{2}}} \right\}}} \\ {= {L_{1}{C_{1}\left( {1 + N} \right)}\left\{ {1 - \frac{L_{1}L_{2}C_{1}C_{2}}{\left( {L_{1}C_{1}} \right)^{2}\left( {1 + N} \right)^{2}}} \right\}}} \\ {\cong {L_{1}{C_{1}\left( {1 + N} \right)}\left\{ {1 - {\frac{L_{2}C_{2}}{L_{1}C_{1}} \cdot \frac{1}{\left( {1 + N} \right)^{2}}}} \right\}}} \\ {\cong {{L_{1}{C_{1}\left( {1 + N} \right)}} - \frac{L_{2}C_{2}}{\left( {1 + N} \right)^{2}}}} \end{matrix}$ $\frac{\partial\omega^{2}}{\partial C_{1}} \cong {L_{1}\left( {1 + N} \right)}$ ${\frac{\partial\omega^{2}}{\partial C_{2}} \cong {{- L_{2}}\frac{1}{\left( {1 + N} \right)^{2}}}} = {{- \frac{N}{\left( {1 + N} \right)^{2}}}L_{1}}$ ${\frac{{\partial\omega^{2}}/{\partial C_{1}}}{{\partial\omega^{2}}/{\partial C_{2}}} \cong \frac{L_{1}\left( {1 + N} \right)}{{- \frac{N}{\left( {1 + N} \right)^{2}}}L}} = {{- \frac{\left( {1 + N} \right)}{\frac{N}{\left( {1 + N} \right)^{2}}}} \cong \left( {1 + N} \right)^{2}}$

FIG. 5 is a schematic diagram of a phase locked loop device of an embodiment of the invention. PFD unit 51 receives a reference clock signal REF_CK and a feedback clock signal FBK_CK and measures the phase and frequency difference therebetween to output phase difference signals, UP and DN. Charging pump circuit 52 receives and transforms the phase difference signals UP and DN into a current to charge loop filter 53. The loop filter 53 receives the current from charging pump circuit to limit the rate of change of a capacitor voltage, VCON, resulting in slow rising or falling voltage corresponding to the phase and frequency difference. The voltage controlled oscillator (VCO) 54 generates an output clock signal according to the voltage VCON. The voltage controlled oscillator 54 comprises a first inductor and a second inductor, and the inductance of the first inductor is N times the inductance of the second inductor. Two embodiments of the voltage controlled oscillator 54 are illustrated with the oscillators shown in the FIG. 2 and FIG. 3. Feedback divider 55 has a parameter M to generate the feedback clock signal FBK_CK with wider range frequency, wherein the frequency of the feedback clock signal FBK_CK is M times the frequency of the output clock signal. In an ideal situation, when the PLL is in an in-lock state, the phase difference signal UP synchronizes to the phase difference signal DN.

While the invention has been described by way of example and in terms of preferred embodiment, it is to be understood that the invention is not limited thereto. To the contrary, it is intended to cover various modifications and similar arrangements (as would be apparent to those skilled in the art). Therefore, the scope of the appended claims should be accorded the broadest interpretation so as to encompass all such modifications and similar arrangements. 

1. A voltage controlled oscillator, comprising: a first capacitor; a first transformer coupled to the first capacitor; a second transformer coupled to the first transformer, wherein the ratio of the second transformer is a predetermined number of times the value of the first transformer; and a negative resistance element coupled to the second transformer to provide a negative resistance.
 2. The oscillator as claimed in claim 1, wherein the first capacitor is a voltage controlled capacitor.
 3. The oscillator as claimed in claim 1, wherein the second transformer includes two portions, further comprising: a first clock output terminal, coupled to the first portion of the transformer, to output a first clock signal; and a second clock output terminal, coupled to the second portion of the second transformer, to output a second clock signal.
 4. The oscillator as claimed in claim 3, wherein the negative resistance element comprises: a first transistor comprising a first input terminal coupled to the first clock output terminal, a first output terminal, and a first control terminal coupled to the second clock output terminal; and a second transistor comprising a second input terminal coupled to the second clock output terminal, a second output terminal coupled to the first output terminal, and a second control terminal coupled to the first clock output terminal.
 5. The oscillator as claimed in claim 4, further comprising a resistor coupled between the first output terminal and ground.
 6. The oscillator as claimed in claim 4, wherein the first control terminal is further coupled to a first buffer, and the second control terminal is further coupled to a second buffer.
 7. The oscillator as claimed in claim 1, wherein the first transformer is further coupled to a voltage regulator. 8-14. (canceled)
 15. The oscillator as claimed in claim 1, wherein the oscillator is further integrated in a phase locked loop device, including: a PFD unit measuring a phase difference and a frequency difference between a reference clock signal and a feedback clock signal of the PLL device to output a difference signal UP and a difference signal DN; a charging pump circuit receiving and transforming the difference signals UP and DN into a current; and a loop filter receiving and transforming the current into a voltage; wherein the oscillator then receiving the voltage and outputting an output signal. 